Floating Tristate Double Boost Converter and a Modification
FELIX A. HIMMELSTOSS
Faculty of Electronic Engineering and Entrepreneurship,
University of Applied Sciences Technikum Wien,
Hoechstaedtplatz 6, 1200 Vienna,
AUSTRIA
Abstract: - Two concepts are combined in this paper. First, the tristate concept, where the electronic switch of a
DC/DC converter is replaced by a combination of two electronic switches and an additional diode. This leads to
two interesting features: first the voltage-transformation ratio can be linearized and second the system can be
transferred into a phase minimum system, which makes the control easier. The second two tristate Boost
converters are combined to a floating double Boost converter. The basic function of the converter is explained.
The large and the linearized small signal models are derived, transfer functions calculated, and Bode plots
drawn. The dynamic behavior is studied with transfer functions and by circuit simulations done with LTSpice.
The inrush is studied and a modification of the converter is shown to avoid dangerous overcurrents.
Key-Words: - Boost converter, floating converter, tristate converter, modified converter, modeling, large signal
model, linearization, small signal model, transfer function.
Received: March 17, 2023. Revised: December 11, 2023. Accepted: December 23, 2023. Published: December 31, 2023.
1 Introduction
The starting point of these investigations is the
floating double Boost converter as shown in
Figure 1.
Fig. 1: Floating double Boost converter
The converter consists of two Boost converters,
each realized by a coil, a switch, a diode, and a
capacitor. The two converters are connected in
parallel at the input and work in series at the output.
At terminals 1 and 2 the input voltage source is
connected. The load is applied to the terminals 3 and
4. One can immediately see that the output voltage
is given by the voltage across the two output
capacitors of the two Boost converters minus the
input voltage:
1212 UUUU CC
. (1)
The voltage-time balance across the inductors
(we use a symmetrical design and control both
active switches with the same duty cycle) in the
steady state is given by:
dUUdU C 1
11
(2)
which leads to the voltage across the capacitors:
d
U
UU CC
11
21
. (3)
With (1) and (3) the voltage transformation ratio is
obtained according to:
d
d
U
U
M
1
1
1
2
. (4)
The circuit diagram of the floating double Boost
converter can be found in [1], [2], [3], [4], [5]. In
[1], the converter is used for a photovoltaic system
and combined with a robust control. The application
shown in [2], is a combined fuel-cell and
supercapacitor system. In [3], an observer system is
applied to the converter. [4], shows again fuel cells
as a supply and in [5], the converter supplies a DC
micro-grid. In [6], [7] and [8], the converter is
combined with the interleaved concept for each
Boost part. [9], uses additional resonant circuits. In
[10], the diodes are replaced by electronic switches.
So a bidirectional operation is possible.
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
298
2 Floating Tristate Double Boost
Converter
The floating double converter concept (one can use
other converter stages instead of the Boost) is now
combined with the tristate concept. Here the active
switch is replaced by a series connection of two
active switches S1, S2, and a diode D1 which is
joined to the connection point of the two electronic
switches. The other terminal of the diode is
connected to the coil. Figure 2 shows this concept
applied to the floating double-boost converter. The
tristate concept goes back to [11], and is deepened
in [12] and [13]. The concept can be extended to a
bidirectional one, [14], [15]. So energy flow in both
directions is possible and the onward losses can be
reduced. An improvement to reduce the switching
losses is presented in [16]. The tristate concept is
mainly applied to the Boost converter. In [17], the
tristate concept is not only applied to the Buck and
the Boost converters, but also to the Buck-Boost, the
Cuk, the Sepic, the Zeta, the D-square, the (2d-
1)/(1-d), and to the improved super-lift Boost
converters.
Fig. 2: Floating tristate double Boost converter
In the continuous inductor current mode, the
tristate converter has three modes. In mode M1 both
active switches are turned on and the input voltage
is across the inductor, in mode M2 S1 is turned off
and the inductor is short-circuited by S2 and D1.
The current through the coil stays now nearly
constant. In mode M3 S2 is off and only D2 is on.
Now a negative voltage is across the coil and the
current through it decreases.
The voltage-time balance of a Boost part can be
written according to:
2111 1dUUdU C
(5)
which leads to the voltage transformation ratio:
2
21
11
1
d
dd
U
UC
. (6)
The voltage transformation ratio of the whole
converter is therefore:
2
21
2
21
1
21
21
1
1
1
2d
dd
d
dd
U
U
(7)
with the limitation
12 dd
. (8)
The voltage transformation ratio with constant
duty cycle d2 and variable duty cycle d1 is shown in
Figure 3. The transformation ratio is linearized and
higher compared to the normal floating double boost
converter (FDBC) without the tristate concept.
Fig. 3: Floating tristate double Boost converter,
voltage transformation ratio: duty cycle of S2 as a
parameter and duty cycle of S1 as independent
variable
The voltage transformation ratio with constant
duty cycle d1 and variable duty cycle d2 is shown in
Figure 4. The transformation is lower compared to
the normal floating double boost converter (FDBC)
without the tristate concept, and the curvature is
smaller.
Fig. 4: Floating tristate double Boost converter,
voltage transformation ratio: duty cycle of S1 as a
parameter and duty cycle of S2 as independent
variable
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
299
Figure 5 shows the converter in the steady state.
The current through the coils and the load current
are shown in the upper graph. In the lower graph the
output, the input voltages, and the control signals of
the switches are shown. The two converter stages
are controlled in an interleaved way, the signals of
the second stage are shifted by 180 compared to
those of the other stage.
The tristate converter suffers again from the
inrush current when applied to a stiff input voltage.
The inrush is equal to the one of the normal floating
double Boost converter.
Fig. 5: Tristate floating Boost converter, up to
down: Current through L1 (red), current through L2
(violet), load current (brown); output voltage
(green), the control signal of S2_2 (dark green,
shifted), the control signal of S1_2 (grey, shifted);
control signal of S2_1 (black), the control signal of
S1_1 (turquoise)
3 Model of the Converter
3.1 State-space Models
The two stages are built similarly and both converter
stages are controlled by the same duty cycles. The
converter can now be described by a second-order
system! So it is not necessary to distinguish between
the inductors and the capacitors, one can write only
L for the coils and C for the capacitors. The load
current can be written according to:
R
uu
iC
LOAD 1
2
. (9)
During mode M1 both active switches of the
stages are turned on and the state equations for the
change of the current through the inductors and the
change of the voltage across the capacitors are:
L
u
dt
diL1
,
C
Ruu
dt
du CC /2 1
. (10)
For the mode M2 (S1 is turned off and D1 turns
on) one gets:
0
dt
diL
,
C
Ruu
dt
du CC /2 1
. (11)
When the second electronic switch S2 is turned off,
D2 turns on and D1 turns off, and the describing
state equations are:
L
uu
dt
di C
L
1
,
C
Ruui
dt
du CLC /2 1
.
(12)
To get the weighted model of the converter one has
to weigh the equations of the three modes by d1, d2-
d1, and 1-d2, respectively, and add them. This leads
to the large signal model:
1
21
2
2
1
1
2
1
1
0u
RC
L
dd
u
i
RCC
dL
d
u
i
dt
d
C
L
C
L
.(13)
Linearizing leads to the small signal model:
2
1
1
0
100102010
2
2
0
1
1
2
1
1
0
d
d
u
C
I
RC
L
UU
L
U
L
DD
u
i
RCC
DL
D
u
i
dt
d
L
C
C
L
C
L
. (14)
The connections at the operating point are:
011 102010020 UDDUD C
(15)
resulting in:
10
20
2010
01
1U
D
DD
UC
(16)
0
12
1100020 U
R
U
R
ID CL
(17)
leading to:
2020
100
011
2
D
I
DR
UU
ILOADC
L
. (18)
Using abbreviations for the elements of the state
and the input matrixes leads to the Laplace
transformed system for the coil current and the
voltage across the capacitors in the s-domain
according to:
)(
)(
)(
0)(
)(
2
1
1
2321
131211
2221
12
sD
sD
sU
BB
BBB
sU
sI
AsA
As
C
L
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
300
(19)
The output voltage is given (in the time-domain) by:
12 120 u
u
i
uC
L
. (20)
All six possible describing transfer functions have
the same denominator:
2
2
211222
2
sAAsAsDen
(21)
The damping factor and the angular resonant
frequency can now be written by:
2
22
A
and
2
2112
AA
(22)
and with the parameters of the converter to:
RC
1
and
22
20 1
1
CR
LC
D
. (23)
The smaller R and C the better the system is
damped and the ringing is reduced.
The parameters of the converter are L=47 µH,
C=330 µF, R=6.25 Ω, and the working point is
described by U10=24 V, UC0=39.8 V, IL0=17.5 A,
D10=0.33, D20=0.5. All Bode plots and step
responses are calculated with these values. The
damping factor is
484
1 RC
and the angular
frequency is
1
s3986
and the frequency 634 Hz.
3.2 Transfer Functions
Now the numerators of the transfer functions have
to be calculated.
3.2.1 UC(s) in Dependence on D1(s)
The numerator can be found by:
1221
21
12
0
1_ BA
A
Bs
UCDNum
. (24)
The transfer function is a simple second-order
phase-minimum system and the phase tends
asymptotically to -180o. The damped ringing is
caused by the poles. Figure 6 shows the Bode plot
and Figure 7 the step response. The resonance is in
good coincidence with the calculation.
Fig. 6: Transfer function between capacitor voltage
and duty cycle of switch S1: Bode plot (solid line:
gain response, dotted line: phase response)
Fig. 7: Transfer function between capacitor voltage
and duty cycle of switch S1: step response (1 %)
3.2.2 UC(s) in dependence on D2(s)
The numerator is now a first-order function
132123
2321
13
2_ BABs
BA
Bs
UCDNum
. (25)
B23 is negative. The zero is therefore on the
right side of the complex plane
LI
DUU
B
BA
s
L
C
Z0
20100
23
1321 1
(26)
and the converter is, like other step-up converters,
described by a non-phase minimum system.
The zero on the right side shifts the phase of the
system to another -90 at high frequencies to -270o
and leads to a slower controlled system. The higher
the value of the coil, the nearer the zero at the
imaginary axis, and the greater the influence of the
zero. Figure 8 shows the Bode plot and Figure 9 the
step response for a change of the duty cycle of 1 %.
The response starts first in the wrong direction, the
voltage reduces first and increases a little bit later.
This is typical for systems with zeros on the right
side.
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
301
Fig. 8: Transfer function between capacitor voltage
and duty cycle of switch S2: Bode plot (solid line:
gain response, dotted line: phase response)
Fig. 9: Transfer function between capacitor voltage
and duty cycle of switch S2: step response (1 %)
For a simpler control (the plant is a phase
minimum system) it is useful to control the
converter with d1 and d2 fixed. The duty cycle of
S1 must be lower than or equal to the duty cycle of
S2.
3.2.3 UC(s) in Dependence on U1(s)
The numerator of the transfer function between the
voltage across the capacitor and the input voltage:
112121
2121
11
1_ BABs
BA
Bs
UCUNum
(27)
leads to a zero on the left side of the complex plane
at :
L
RDUU
B
BA
sC
Z20100
21
1121 1
(28)
and to a phase minimum system. The phase tends
now to only -90o at higher frequencies. Figure 10
shows the Bode plot and Figure 11 the step
response.
This transfer function is especially necessary
when a disturbance feedforward is applied.
Fig. 10: Transfer function between capacitor voltage
and the input voltage: Bode plot (solid line: gain
response, dotted line: phase response)
Fig. 11: Transfer function between capacitor voltage
and the input voltage: step response (1 V)
Sometimes the control of the current through the
coil is of importance e.g. by using the converter for
supplying light emitting diodes, or when using a
two-loop control.
3.2.4 IL(s) in Dependence on D1(s)
The numerator of the current through the inductor
and the duty cycle of switch S1 can be calculated
according to:
122212
22
1212
0
1_ BAsB
As
AB
ILDNum
. (29)
The zero is at:
CR
AsZ2
22
(967 s-1, 154 Hz) (30)
and is at the left side of the complex plane and the
phase tends now to only -90o. The control is
therefore easy. Figure 12 shows the Bode plot and
Figure 13 the step response.
Fig. 12: Transfer function between the current
through the coil and the duty cycle of switch S1:
Bode plot (solid line: gain response, dotted line:
phase response)
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
302
Fig. 13: Transfer function between the current
through the coil and the duty cycle of switch S1:
step response (1 %)
3.2.5 IL(s) in Dependence on D2(s)
The numerator of the transfer function between the
current through the coil and the duty cycle of switch
S2 can be found in
2312132213
2223
1213
2_ BABAsB
AsB
AB
ILDNum
(31)
The zero lies at
CUU
ID
RCB
BABA
s
C
L
Z100
02
13
23121322 1
2
(32)
and again the transfer function describes a phase
minimum system. Figure 14 shows the Bode plot
and Figure 15 shows the step response.
Fig. 14: Transfer function between the current
through the coil and the duty cycle of switch S2:
Bode plot (solid line: gain response, dotted line:
phase response)
Fig. 15: Transfer function between the current
through the coil and the duty cycle of switch S2:
step response (1 %)
3.2.6 IL(s) in Dependence on U1(s)
The numerator of the transfer function between the
current through the coils and the input voltage is
obtained by:
2112112211
2221
1211
1_ BABAsB
AsB
AB
ILUNum
(33)
The zero is again on the left side at
CRDD
D
RCB
BABA
sZ2010
20
11
21121122 1
12
2
. (34)
Figure 16 shows the Bode plot and Figure 17
the step response.
Fig. 16: Transfer function between the current
through the coil and the input voltage: Bode plot
(solid line: gain response, dotted line: phase
response)
Fig. 17: Transfer function between the current
through the coil and the input voltage: step response
(1 V)
The control of the current is easy for all three
input variables and can be done by a PI controller.
In a two-loop control, only a P-controller for the
inner current loop is necessary. More results are
shown in section 6.
4 Inrush
A very important aspect of a converter is its inrush
current when the input voltage is applied. This is
especially important when the input source is stable
and can deliver a large current.
Figure 18 shows an inrush when the converter is
applied at 24 V (the used converter parameters are
L1=L2=47 µH, C1=C2=330 µF). The input voltage
goes up within 10 µs. The currents through the coils
rise nearly sinusoidal (damped by the load resistor),
and when the current reaches zero the diodes turn
off. The voltage across the capacitors rises to nearly
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
303
double the input voltage, then the capacitors are
discharged by the load (with an exponential
function). When the voltage across a capacitor is
lower than the input voltage by a forward voltage of
the diode, the diode turns on and recharges the
capacitor with a damped sinusoidal waveform. The
current through the load is supplied by both
converter stages. From the load current one can
imply that the output voltage is negative at the
beginning.
Fig. 18: Tristate floating double Boost converter:
inrush with load resistor 6.25 Ω, up to down: load
current (brown); current through L2 (violet); current
through L1 (red); voltage across C1 (green), input
voltage (blue)
Figure 19 shows the inrush when no load is
connected to the converter. The converter
parameters are the same as for Figure 18. The
current through the inductors are sinusoidal half-
waves. The voltage across the load becomes
negative until the capacitors are charged so that they
can compensate for the input voltage. The voltage
across the capacitors reaches nearly two times the
input voltage. (Without losses across the diode and
the series resistors of the coil and the capacitor, it
would reach double the input voltage exactly).
Fig. 19: Tristate floating double Boost converter:
inrush with no load, up to down: output voltage
(turquoise); current through L2 (violet); current
through L1 (red); voltage across C1 (green), input
voltage (blue)
This converter has a large inrush current when
connected to a stiff input voltage, as are batteries
and DC microgrids. The inrush current is two times
the resonant current of the resonant circuit formed
by the coil and the capacitor of a converter leg
leading to
1
2U
L
C
IIN
. (35)
One should also keep in mind that the inductor
will saturate and decrease and so the current will get
much higher!
With an additional input transistor SIN which
starts with a duty cycle from zero and increases to
one by a ramp function, the current into the
converter can be reduced and controlled. This
additional transistor SIN can also be used as a fuse
to turn off the converter very fast in the case of a
short-circuit, open circuit, overcurrent, or overheat.
Between the drain of the transistor SIN and the
anode of the additional diode DIN, an input
capacitor CIN has to be connected (Figure 20).
Figure 21 shows the turn-on with no load and
Figure 22 with load. The current through L1 is
depicted, the current through the other coil looks
equal, and the input current is therefore double as
large. The output voltage, the voltages across the
capacitors, and the input voltage are also shown in
these figures. No dangerous current occurs, but the
output voltage is negative again at the beginning.
Fig. 20: Pre-stage to avoid the inrush and to serve as
an electronic fuse
Fig. 21: Floating double Boost with additional
inrush current reduction (no load), up to down:
current through the first coil (red); output voltage
(dark green); the voltage across the second capacitor
(turquoise); input voltage (blue), voltage across the
first capacitor (green)
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
304
Fig. 22: Floating double Boost with additional
inrush current reduction (with load), up to down:
current through the first coil (red); output voltage
(dark green); the voltage across the second
capacitor(turquoise); input voltage (blue), the
voltage across the first capacitor (green)
5 Floating Tristate Modified Double
Boost Converter
5.1 Circuit
Another way to avoid the large inrush current is to
modify the Boost stages. Instead of connecting the
capacitors across the output of the Boost stages, one
has to connect them between input and output as
shown in Figure 23.
Fig. 23: Floating tristate modified double Boost
converter
5.2 Inrush
Figure 24 shows the currents through the coils, the
input, and the load. There is only a small ringing
and no dangerous current. The function is the same
as was shown for the basic structure, but the input
current is changed and the voltage stress across the
capacitors is reduced to the difference between
output and input voltages of the respective Boost
parts. No negative output voltage occurs.
Fig. 24: Modified tristate floating double Boost
converter with load, up to down: load current
(brown); current through L2 (violet), current
through L1 (red); input voltage (blue), output
voltage (green).
5.3 Model of the Modified Converter
When the position of the capacitors is changed, the
converter is modified. The model of the converter
can be obtained in the same way as for the normal
floating tristate Boost converter according to
Figure 2 and results in:
1
1
2
2
1
2
1
1
0u
RC
L
d
u
i
RCC
dL
d
u
i
dt
d
C
L
C
L
. (36)
Linearizing leads to the small signal model:
2
1
1
0
01010
20
20
0
1
2
1
1
0
d
d
u
C
I
RC
L
U
L
U
L
D
u
i
RCC
DL
D
u
i
dt
d
L
C
C
L
C
L
(37)
which leads to the same transfer functions. Only B11
and B13 change their values.
The output equation:
12 120 u
u
i
uC
L
(38)
leads to the output voltage.
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
305
6 Simulations
To prove the model a comparison with the
simulation of the circuit is done.
Figure 25(a) shows the simulation with the
small signal model with the help of the transfer
functions. The change of the voltage across the
capacitor is shown around the working point. It
starts with a step-up of 1 % for the duty cycle d1,
after 20 ms the d1 goes down by -1 %. After another
20 ms, the duty cycle d2 jumps up by 1 % and
jumps back after 20 ms. After another 20 ms, the
input voltage makes a step of plus 1 V and steps
back after 20 ms. Figure 25(b) shows the results
done by a simulation of the converter circuit. One
can see that the dynamic behavior is very precisely
modeled with the transfer functions. The converter
is switched to 100 kHz and one can see the ripple of
the current (one can see the band within which the
current is changing).
(a)
(b)
Fig. 25: Change of the capacitor voltage caused by
steps every 20 ms, d1 up and down by 0.01, d2 up
and down by 0.01, and U1 up and down by 1 V (up
to down): changes of the current through L1 (red),
current through L1 (red); output current (green),
voltage across C1 (turquoise), input voltage (blue),
a. small signal model, b—circuit simulation
The circuit simulation takes much longer (24
minutes, including 10 ms for the inrush, and 20 ms
for start-up which are not shown in Figure 25) than
the simulation with transfer functions (a few
seconds) on the used computer. Therefore, for the
controller design the linear model would be used to
check the results. The complete circuit simulation
with inrush and soft-start is shown in Figure 26.
Fig. 26: Soft-start, steps of the duty cycle of d1 and
d2 and steps of the input voltage (up to down):
current through L2 (violet), current through L1
(red); output current (green), voltage across C1
(turquoise), input voltage (blue)
7 Conclusion
The combination of the tristate and the floating
double converter concepts leads to a new and
interesting DC/DC converter, especially useful for
fuel-cell and DC-micro-grid supply, with useful
features:
High step-up ratio
Linearization of the voltage transformation
ratio, when the duty cycle of switch S2 is
kept constant and the duty cycle of S1 is the
variable
The converter is a phase-minimum system
in this case
Reduction of the voltage transformation
ratio and smoothing of the characteristics,
when the duty cycle of S1 is kept constant
and the control occurs with the duty cycle of
S2, in this case, the converter is a non-phase
minimum system
Doubling the AC component of the input
current, when the two converter stages are
controlled with 180o shifted signals
Changing the position of the capacitors
according to Figure 23 avoids the inrush,
when the converter is connected to a stiff
input source, like batteries or a stable DC
micro-grid, avoids also a negative output
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
306
voltage during turn-on, and reduces the
voltage stress of the capacitors
Symmetrical design and using the same
duty cycles for the electronic switches in the
two Boost stages reduces the converter to a
second-order system
The second mode of the converter can be
additionally used to control the converter in
the case of errors
The converter can be used also for charging
batteries and to supply light-emitting diodes. In this
case, an inductor should be connected in series to
the load and the current through it has to be
controlled. The floating output voltage can be used
as the input of an isolated converter, e.g. a two-
switch forward or flyback converter. It should be
mentioned that the concept can be extended into a
bidirectional system when the electronic switches
and the diodes are replaced by current-bidirectional
switches consisting of an electronic switch and an
antiparallel diode. Furthermore, other tristate
converter types as shown in [17], can be combined
with the floating double converter concept.
References:
[1] M. Miranda, P. Banakar, G. Gunnal and V.
Kiran Kumar, Robust Voltage Control of
Improved Floating Interleaved Boost
Converter for Photovoltaic Systems, 2020
5th International Conference on Computing,
Communication and Security (ICCCS),
Patna, India, 2020, pp. 1-5, doi:
10.1109/ICCCS49678.2020.9276866.
[2] M. Kabalo, D. Paire, B. Blunier, D.
Bouquain, M. G. Simoes and A. Miraoui,
Experimental Validation of High-Voltage-
Ratio Low-Input-Current-Ripple Converters
for Hybrid Fuel Cell Supercapacitor
Systems, IEEE Transactions on Vehicular
Technology, vol. 61, no. 8, pp. 3430-3440,
Oct. 2012, doi: 10.1109/TVT.2012.2208132.
[3] Liangcai Xu; Yigeng Huangfu; Rui Ma;
Shengrong Zhuo; Dongdong Zhao; Jun Zhao;
Fei Gao, Extended State Observer-Based
Sliding-Mode Control for Floating
Interleaved Boost Converters, IECON 2018 -
44th Annual Conference of the IEEE
Industrial Electronics Society, Washington,
DC, USA, 2018, pp. 5283-5289, doi:
10.1109/IECON.2018.8591138.
[4] Qian Li; Yigeng Huangfu; Liangcai Xu;
Jiang Wei; Rui Ma; Dongdong Zhao; Fei
Gao, An Improved Floating Interleaved
Boost Converter With the Zero-Ripple Input
Current for Fuel Cell Applications, IEEE
Transactions on Energy Conversion, vol. 34,
no. 4, pp. 2168-2179, Dec. 2019, doi:
10.1109/TEC.2019.2936416.
[5] P. Lin, W. Jiang, J. Wang, D. Shi, C. Zhang
and P. Wang, Toward Large-Signal
Stabilization of Floating Dual Boost
Converter-Powered DC Microgrids Feeding
Constant Power Loads, IEEE Journal of
Emerging and Selected Topics in Power
Electronics, vol. 9, no. 1, pp. 580-589, Feb.
2021, doi: 10.1109/JESTPE.2019.2956097.
[6] M. G. Simões, C. L. Lute, A. N. Alsaleem,
D. I. Brandao and J. A. Pomilio,
Bidirectional floating interleaved buck-boost
DC-DC converter applied to residential PV
power systems, 2015 Clemson University
Power Systems Conference (PSC), Clemson,
SC, USA, 2015, pp. 1-8, doi:
10.1109/PSC.2015.7101675.
[7] D. Coutellier, V. G. Agelidis and S. Choi,
Experimental verification of floating-output
interleaved-input DC-DC high-gain
transformer-less converter topologies, 2008
IEEE Power Electronics Specialists
Conference, Rhodes, Greece, 2008, pp. 562-
568, doi: 10.1109/PESC.2008.4591989.
[8] M. Kabalo, B. Blunier, D. Bouquain and A.
Miraoui, Comparaison analysis of high
voltage ratio low input current ripple floating
interleaving boost converters for fuel cell
applications, 2011 IEEE Vehicle Power and
Propulsion Conference, Chicago, IL, USA,
2011, pp. 1-6, doi:
10.1109/VPPC.2011.6043101.
[9] H. Sartipizadeh, F. Harirchi, M. Babakmehr
and P. Dehghanian, Robust Model Predictive
Control of DC-DC Floating Interleaved
Boost Converter With Multiple
Uncertainties, in IEEE Transactions on
Energy Conversion, vol. 36, no. 2, pp. 1403-
1412, June 2021, doi:
10.1109/TEC.2021.3058524.
[10] P. Lin, W. Jiang, J. Wang, D. Shi, C. Zhang
and P. Wang, Toward Large-Signal
Stabilization of Floating Dual Boost
Converter-Powered DC Microgrids Feeding
Constant Power Loads, IEEE Journal of
Emerging and Selected Topics in Power
Electronics, vol. 9, no. 1, pp. 580-589, Feb.
2021, doi: 10.1109/JESTPE.2019.2956097.
[11] K. Viswanathan, R. Oruganti and D.
Srinivasan, Tri-state boost converter with no
right half plane zero, 4th IEEE International
Conference on Power Electronics and Drive
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
307
Systems. IEEE PEDS 2001 - Indonesia.
Proceedings (Cat. No.01TH8594), Denpasar,
Indonesia, 2001, pp. 687-693 vol.2, doi:
10.1109/PEDS.2001.975402.
[12] K. Viswanathan, R. Oruganti and D.
Srinivasan, A novel tri-state boost converter
with fast dynamics, IEEE Transactions on
Power Electronics, vol. 17, no. 5, pp. 677-
683, Sept. 2002, doi:
10.1109/TPEL.2002.802197.
[13] S. K. Viswanathan, R. Oruganti and D.
Srinivasan, Dual mode control of tri-state
boost converter for improved performance,
IEEE 34th Annual Conference on Power
Electronics Specialist, 2003. PESC '03,
Acapulco, Mexico, 2003, pp. 944-950 vol.2,
doi: 10.1109/PESC.2003.1218182.
[14] A. Choubey and L. A. C. Lopes, A tri-state
4-switch bi-directional converter for
interfacing supercapacitors to DC micro-
grids, 2017 IEEE 8th International
Symposium on Power Electronics for
Distributed Generation Systems (PEDG),
Florianopolis, Brazil, 2017, pp. 1-6, doi:
10.1109/PEDG.2017.7972507.
[15] Q. Wang and L. A. C. Lopes, Multi-Mode
PWM Modulator for a 4-Switch DC-DC
Converter Operating with Tri-State, 2023
IEEE 17th International Conference on
Compatibility, Power Electronics and Power
Engineering (CPE-POWERENG), Tallinn,
Estonia, 2023, pp. 1-6, doi: 10.1109/CPE-
POWERENG58103.2023.10227409.
[16] O. Knecht, D. Bortis and J. W. Kolar, ZVS
Modulation Scheme for Reduced Complexity
Clamp-Switch TCM DC–DC Boost
Converter, IEEE Transactions on Power
Electronics, vol. 33, no. 5, pp. 4204-4214,
May 2018, doi:
10.1109/TPEL.2017.2720729.
[17] F. A. Himmelstoss, Tristate Converters,
WSEAS Transactions on Power Systems,
Vol. 18, 2023, pp. 259-269,
https://doi.org/10.37394/232016.2023.18.27.
Contribution of Individual Authors to the
Creation of a Scientific Article (Ghostwriting
Policy)
The author contributed to the present research, in all
stages from the formulation of the problem to the
final findings and solution.
Sources of Funding for Research Presented in a
Scientific Article or Scientific Article Itself
No funding was received for conducting this study.
Conflict of Interest
The author has no conflicts of interest to declare.
Creative Commons Attribution License 4.0
(Attribution 4.0 International, CC BY 4.0)
This article is published under the terms of the
Creative Commons Attribution License 4.0
https://creativecommons.org/licenses/by/4.0/deed.en
_US
WSEAS TRANSACTIONS on CIRCUITS and SYSTEMS
DOI: 10.37394/23201.2023.22.30
Felix A. Himmelstoss
E-ISSN: 2224-266X
308